110 MSPS/140 MSPS
Analog Interface for Flat Panel Displays
AD9985A
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113
2005 Analog Devices, Inc. All rights reserved.
FEATURES
Variable analog input bandwidth control
Variable SOGIN bandwidth control
Automated clamping level adjustment
140 MSPS maximum conversion rate
300 MHz analog bandwidth
0.5 V to 1.0 V analog input range
500 ps p-p PLL clock jitter at 110 MSPS
3.3 V power supply
Full sync processing
Selectable input filtering
Sync detect for hot plugging
Midscale clamping
Power-down mode
Low power: 500 mW typical
4:2:2 output format mode
APPLICATIONS
RGB graphics processing
LCD monitors and projectors
Plasma display panels
Scan converters
Microdisplays
Digital TVs
FUNCTIONAL BLOCK DIAGRAM
R
IN
R
OUTA
G
IN
G
OUTA
B
IN
B
OUTA
MIDSCV
SYNC
PROCESSING
AND CLOCK
GENERATION
DTACK
HSOUT
VSOUT
SOGOUT
REF
REF
BYPASS
SERIAL REGISTER AND
POWER MANAGEMENT
SCL
SDA
A0
SOGIN
FILT
CLAMP
COAST
HSYNC
AD9985A
CLAMP
8
A/D
CLAMP
8
A/D
CLAMP
8
A/D
05484-001
AUTO-CLAMP
LEVEL ADJUST
AUTO-CLAMP
LEVEL ADJUST
AUTO-CLAMP
LEVEL ADJUST
Figure 1.
GENERAL DESCRIPTION
The AD9985A is a complete 8-bit, 140 MSPS, monolithic
analog interface optimized for capturing RGB graphics signals
from personal computers and workstations. Its 140 MSPS
encode rate capability and full power analog bandwidth of 300
MHz support resolutions up to SXGA (1280 1024 at 75 Hz).
The AD9985A includes a 140 MHz triple ADC with internal
1.25 V reference, a PLL, and programmable gain, offset, and
clamp control. The user provides only a 3.3 V power supply,
analog input, and horizontal sync (Hsync) and Coast signals.
Three-state CMOS outputs can be powered from 2.5 V to 3.3 V.
The AD9985A's on-chip PLL generates a pixel clock from the
Hsync input. Pixel clock output frequencies range from 12 MHz
to 140 MHz. PLL clock jitter is 500 ps p-p typical at 140 MSPS.
When the Coast signal is presented, the PLL maintains its
output frequency in the absence of Hsync. A sampling phase
adjustment is provided. Data, Hsync, and clock output phase
relationships are maintained. The AD9985A also offers full sync
processing for composite sync and sync-on-green applications.
A clamp signal is generated internally or can be provided by the
user through the CLAMP input pin. This interface is fully
programmable via a 2-wire serial interface.
Fabricated in an advanced CMOS process, the AD9985A is
provided in a space-saving 80-lead LQFP surface-mount
Pb-free plastic package, and is specified over the 40C to
+85C temperature range.
AD9985A
Rev. 0 | Page 2 of 32
TABLE OF CONTENTS
Specifications..................................................................................... 3
Explanation of Test Levels ........................................................... 6
Absolute Maximum Ratings............................................................ 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Design Guide................................................................................... 11
General Description................................................................... 11
Digital Inputs .............................................................................. 11
Input Signal Handling................................................................ 11
Hsync, Vsync Inputs .................................................................. 11
Serial Control Port ..................................................................... 11
Output Signal Handling............................................................. 11
Clamping ..................................................................................... 11
RGB Clamping........................................................................ 11
YUV Clamping ....................................................................... 12
Gain and Offset Control............................................................ 12
Auto Offset .............................................................................. 12
Sync-on-Green............................................................................ 13
Clock Generation ....................................................................... 13
12-Bit Divisor Register .......................................................... 14
2-Bit VCO Range Register .................................................... 14
3-Bit Charge Pump Current Register .................................. 14
5-Bit Phase Adjust Register................................................... 14
Power Management.................................................................... 14
Timing.......................................................................................... 15
Hsync Timing ............................................................................. 15
Coast Timing .............................................................................. 16
2-Wire Serial Register Map ........................................................... 17
2-Wire Serial Control Register Detail Chip Identification ... 19
PLL Divider Control .................................................................. 19
Clock Generator Control .......................................................... 20
Clamp Timing............................................................................. 20
Hsync Pulse Width..................................................................... 20
Input Gain ................................................................................... 20
Input Offset ................................................................................. 21
Mode Control 1 .......................................................................... 21
2-Wire Serial Control Port ............................................................ 26
Data Transfer via Serial Interface............................................. 26
Sync Slicer.................................................................................... 28
Sync Separator ............................................................................ 28
PCB Layout Recommendations.................................................... 29
Analog Interface Inputs ............................................................. 29
Power Supply Bypassing ............................................................ 29
PLL ............................................................................................... 29
Outputs (Both Data and Clocks).............................................. 30
Digital Inputs .............................................................................. 30
Voltage Reference ....................................................................... 30
Outline Dimensions ....................................................................... 31
Ordering GuIde .......................................................................... 31
REVISION HISTORY
7/05--Revision 0: Initial Version
AD9985A
Rev. 0 | Page 3 of 32
SPECIFICATIONS
V
D
= 3.3 V, V
DD
= 3.3 V, ADC clock = maximum conversion rate, unless otherwise noted.
Table 1.
AD9985AKSTZ-110
AD9985AKSTZ-140
Parameter Temp
Test
Level
Min
Typ
Max
Min
Typ
Max
Unit
RESOLUTION
8
8
Bits
DC
ACCURACY
Differential Nonlinearity
25C
I
0.5
+1.25/-1.0
0.5
+1.35/-1.0
LSB
Full
VI
+1.35/-1.0
1.45/-1.0
LSB
Integral Nonlinearity
25C
I
0.5
1.85
0.5
2.0
LSB
Full
VI
2.0
2.3
LSB
No Missing Codes
Full
VI
Guaranteed
Guaranteed
ANALOG
INPUT
Input Voltage Range
Minimum Full
VI
0.5
0.5
V
p-p
Maximum Full
VI
1.0
1.0
V
p-p
Gain Tempco
25C
V
100
100
ppm/C
Input Bias Current
25C
IV
1
1
A
Full
IV
1
1
A
Input Offset Voltage
Full
V
7
7
mV
Input Full-Scale Matching
Full
VI
1.5
8.0
1.5
8.0
%FS
Offset Adjustment Range
Full
VI
46
49
52
46
49
52
%FS
REFERENCE
OUTPUT
Output
Voltage
Full V
1.25
1.25
V
Temperature Coefficient
Full
V
50
50
ppm/C
SWITCHING
PERFORMANCE
Maximum Conversion Rate
Full
VI
110
140
MSPS
Minimum Conversion Rate
Full
IV
10
10
MSPS
Data to Clock Skew
Full
IV
-0.5
+2.0
-0.5
+2.0
ns
t
BUFF
Full VI
4.7
4.7
s
t
STAH
Full VI
4.0
4.0
s
t
DHO
Full VI
300
300
ns
t
DAL
Full VI
4.7
4.7
s
t
DAH
Full VI
4.0
4.0
s
t
DSU
Full VI
250
250
ns
t
STASU
Full VI
4.7
4.7
s
t
STOTSU
Full VI
4.0
4.0
s
HSYNC Input Frequency
Full
IV
15
110
15
110
kHz
Maximum PLL Clock Rate
Full
VI
110
140
MHz
Minimum PLL Clock Rate
Full
IV
12
12
MHz
PLL Jitter
25C
IV
400
700
1
400
700
1
ps p-p
Full
IV
1000
1
400
700
1
ps p-p
Sampling Phase Tempco
Full
IV
15
15
ps/C
DIGITAL
INPUTS
Input Voltage, High (V
IH
) Full
VI
2.5
2.5
V
Input Voltage, Low (V
IL
) Full
VI
0.8 0.8 V
Input Current, High (V
IH
) Full
V
-1.0
-1.0 A
Input Current, Low (V
IL
) Full
V
+1.0 +1.0 A
Input Capacitance
25C
V
3
3
pF
AD9985A
Rev. 0 | Page 4 of 32
AD9985AKSTZ-110
AD9985AKSTZ-140
Parameter Temp
Test
Level
Min
Typ
Max
Min
Typ
Max
Unit
DIGITAL
OUTPUTS
Output Voltage, High (V
OH
) Full VI
V
D
- 0.1
V
D
- 0.1
V
Output Voltage, Low (V
OL
) Full VI
0.1
0.1
V
Duty Cycle DATACK
Full
IV
45
50
55
45
50
55
%
Output
Coding
Binary
Binary
POWER
SUPPLY
V
D
Supply Voltage
Full
IV
3.15
3.3
3.45
3.15
3.3
3.45
V
V
DD
Supply Voltage
Full
IV
2.2
3.3
3.45
2.2
3.3
3.45
V
P
VD
Supply Voltage
Full
IV
3.15
3.3
3.45
3.15
3.3
3.45
V
I
D
Supply Current (V
D
) 25C
V 132
180
mA
I
DD
Supply Current (V
DD
)
2
25C V
19
26
mA
IP
VD
Supply Current (P
VD
) 25C
V
8
11
mA
Total Power Dissipation
Full
VI
525
760
650
900
mW
Power-Down Supply Current
Full
VI
5
15
5
15
mA
Power-Down
Dissipation Full VI
16.5 50
16.5 50
mW
DYNAMIC
PERFORMANCE
Analog Bandwidth, Full
Power
25C V
300
300
MHz
Transient Response
25C
V
2
2
ns
Overvoltage Recovery
Time
25C V
1.5
1.5
ns
Signal-to-Noise Ratio (SNR)
25C
V
44
43
dB
(Without Harmonics)
Full
V
43
42
dB
f
IN
= 40.7 MHz
Crosstalk Full
V
55
55
dBc
THERMAL CHARACTERISTICS
JC
Junction-to-Case
Thermal Resistance
V
16
16
C/W
JA
Junction-to-Ambient
Thermal Resistance
V
35
35
C/W
1
VCO range = 10, charge pump current = 110, PLL divider = 1693.
2
DATACK load = 15 pF, data load = 5 pF.
AD9985A
Rev. 0 | Page 5 of 32
V
D
= 3.3 V, V
DD
= 3.3 V, ADC clock = maximum conversion rate, unless otherwise noted.
Table 2.
Test
AD9985ABSTZ-110
Parameter Temp
Level
Min
Typ
Max
Unit
RESOLUTION
8
Bits
DC ACCURACY
LSB
Differential Nonlinearity
25C
I
0.5
+1.25/-1.0
LSB
Full
VI
+1.5/-1.0
LSB
Integral Nonlinearity
25C
I
0.5
1.85
LSB
Full
VI
3.2
ANALOG INPUT
Input Voltage Range
Minimum Full
VI
0.5
V
p-p
Maximum Full
VI
1.0
V
p-p
Gain Tempco
25C
V
100
ppm/C
Input Bias Current
25C
IV
1
A
Full
IV
2
A
Input Offset Voltage
Full
VI
7
mV
Input Full-Scale Matching
Full
VI
1.5
8.0
% FS
Offset Adjustment Range
Full
VI
46
49
52
% FS
REFERENCE OUTPUT
Output Voltage
Full
VI
1.25
V
Temperature Coefficient
Full
V
100
ppm/C
SWITCHING PERFORMANCE
Maximum Conversion Rate
Full
VI
110
MSPS
Minimum Conversion Rate
Full
IV
10
MSPS
Data-to-Clock Skew
Full
IV
-0.5
+2.0
ns
t
BUFF
Full VI 4.7
s
t
STAH
Full VI 4.0
s
t
DHO
Full VI 300
ns
t
DAL
Full VI 4.7
s
t
DAH
Full VI 4.0
s
t
DSU
Full VI 250
ns
t
STASU
Full VI 4.7
s
t
STAH
Full VI
s
HSYNC Input Frequency
Full
IV
15
110
kHz
Maximum PLL Clock Rate
Full
VI
110
MHz
Minimum PLL Clock Rate
Full
IV
12
MHz
PLL Jitter
25C
IV
400
700
1
ps p-p
Full
IV
1000
1
ps p-p
Sampling Phase Tempco
Full
IV
15
ps/C
DIGITAL INPUTS
Input Voltage, High (V
IH
) Full
VI
2.5
V
Input Voltage, Low (V
IL
) Full
VI
0.8
V
Input Current, High (I
IH
) Full
V
-1.0
A
Input Current, Low (I
IL
) Full
V
1.0
A
Input Capacitance
25C
V
3
pF
DIGITAL OUTPUTS
Output Voltage, High (V
OH
) Full
VI
V
D
- 0.1
V
Output Voltage, Low (V
OL
) Full
VI
0.1
V
Duty Cycle, DATACK
Full
IV
45
50
55
%
Output Coding
Binary
AD9985A
Rev. 0 | Page 6 of 32
Test
AD9985ABSTZ-110
Parameter Temp
Level
Min
Typ
Max
Unit
POWER SUPPLY
V
D
Supply Voltage
Full
IV
3.15
3.3
3.45
V
V
DD
Supply Voltage
Full
IV
2.2
3.3
3.45
V
P
VD
Supply Voltage
Full
IV
3.15
3.3
3.45
V
I
D
Supply Current (V
D
) 25C
V
132
mA
I
DD
Supply Current (V
DD
)
2
25C V
19
mA
IP
VD
Supply Current (P
VD
) 25C
V
8
mA
Total Power Dissipation
Full
VI
525
760
mW
Power-Down Supply Current
Full
VI
5
15
mA
Power-Down Dissipation
Full
VI
16.5
50
mW
DYNAMIC PERFORMANCE
Analog Bandwidth, Full Power
25C
V
300
MHz
Transient Response
25C
V
2
ns
Overvoltage Recovery Time
25C
V
1.5
ns
Signal-to-Noise Ratio (SNR)
25C
V
44
dB
(Without Harmonics)
Full
V
43
dB
f
IN
= 40.7 MHz
Crosstalk Full
V
55
dBc
THERMAL CHARACTERISTICS
JC
Junction-to-Case
Thermal Resistance
V
16
C/W
JA
Junction-to-Ambient
Thermal Resistance
V
35
C/W
1
VCO range = 10, charge pump current = 110, PLL divider = 1693.
2
DATACK load = 15 pF, data load = 5 pF.
EXPLANATION OF TEST LEVELS
I.
100% production tested.
II.
100% production tested at 25C and sample tested at specified temperatures.
III.
Sample tested only.
IV.
Parameter is guaranteed by design and characterization testing.
V.
Parameter is a typical value only.
VI.
100% production tested at 25C; guaranteed by design and characterization testing.
AD9985A
Rev. 0 | Page 7 of 32
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter Rating
V
D
3.6 V
V
DD
3.6 V
Analog Inputs
V
D
to 0.0 V
Digital Inputs
5 V to 0.0 V
Digital Output Current
20 mA
Operating Temperature
-40C to +85C
Storage Temperature
-65C to +150C
Maximum Junction Temperature
150C
Maximum Case Temperature
150C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum ratings for extended periods may affect device
reliability.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the
human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
AD9985A
Rev. 0 | Page 8 of 32
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
2
GREEN <7>
3
GREEN <6>
4
GREEN <5>
7
GREEN <2>
6
GREEN <3>
5
GREEN <4>
1
GND
8
GREEN <1>
9
GREEN <0>
10
GND
12
BLUE <7>
13
BLUE <6>
14
BLUE <5>
15
BLUE <4>
16
BLUE <3>
17
BLUE <2>
18
BLUE <1>
19
BLUE <0>
20
GND
11
V
DD
59
58
57
54
55
56
60
53
52
V
D
REF BYPASS
SDA
R
IN
A0
SCL
GND
GND
V
D
51
V
D
49
SOGIN
48
G
IN
47
GND
46
V
D
45
V
D
44
GND
43
B
IN
42
V
D
41
GND
50
GND
21
GND
22
V
DD
23
V
DD
24
GND
25
GND
26
V
D
27
V
D
28
GND
29
COAS
T
30
H
SYN
C
31
VSYN
C
32
GND
33
FILT
34
PV
D
35
PV
D
36
GND
37
MI
DS
CV
38
CLAMP
39
V
D
40
GND
80
GND
79
V
DD
78
V
DD
77
RE
D <
0
>
76
RE
D <
1
>
75
RE
D <
2
>
74
RE
D <
3
>
73
RE
D <
4
>
72
RE
D <
5
>
71
RE
D <
6
>
70
RE
D <
7
>
69
V
DD
68
GND
67
DATACK
66
HS
OUT
65
SOGOUT
64
VSOU
T
63
GND
62
V
D
61
GND
PIN 1
AD9985A
TOP VIEW
(Not to Scale)
05484-002
Figure 2. Pin Configuration
Table 4. Complete Pinout List
Pin Type
Mnemonic
Function
Value
Pin No.
Inputs R
IN
Analog Input for Converter R
0.0 V to 1.0 V
54
G
IN
Analog Input for Converter G
0.0 V to 1.0 V
48
B
B
IN
Analog Input for Converter B
0.0 V to 1.0 V
43
HSYNC
Horizontal SYNC Input
3.3 V CMOS
30
VSYNC
Vertical SYNC Input
3.3 V CMOS
31
SOGIN
Input for Sync-on-Green
0.0 V to 1.0 V
49
CLAMP
Clamp Input (External Clamp Signal)
3.3 V CMOS
38
COAST
PLL Coast Signal Input
3.3 V CMOS
29
Outputs
Red [7:0]
Outputs of Converter Red, Bit 7 is the MSB
3.3 V CMOS
70 to 77
Green [7:0]
Outputs of Converter Green, Bit 7 is the MSB
3.3 V CMOS
2 to 9
Blue [7:0]
Outputs of Converter Blue, Bit 7 is the MSB
3.3 V CMOS
12 to 19
DATACK
Data Output Clock
3.3 V CMOS
67
HSOUT
HSYNC Output (Phase-Aligned with DATACK)
3.3 V CMOS
66
VSOUT
VSYNC Output (Phase-Aligned with DATACK)
3.3 V CMOS
64
SOGOUT
Sync-on-Green Slicer Output
3.3 V CMOS
65
References REF
BYPASS
Internal Reference Bypass
1.25 V
58
MIDSCV
Internal Midscale Voltage Bypass
37
FILT
Connection for External Filter Components
for Internal PLL
33
AD9985A
Rev. 0 | Page 9 of 32
Pin Type
Mnemonic
Function
Value
Pin No.
Power Supply
V
D
Analog Power Supply
3.3 V
26, 27, 39, 42, 45, 46, 51, 52, 59, 62
V
DD
Output Power Supply
3.3 V
11, 22, 23, 69, 78, 79
PV
D
PLL Power Supply
3.3 V
34, 35
GND
Ground
0
V
1, 10, 20, 21, 24, 25, 28, 32, 36, 40, 41,
44, 47, 50, 53, 60, 61, 63, 68, 80
Serial Port (2-Wire)
SDA
Serial Port Data I/O
3.3 V CMOS
57
SCL
Serial Port Data Clock (100 kHz maximum)
3.3 V CMOS
56
A0
Serial Port Address Input 1
3.3 V CMOS
55
Table 5. Pin Function Descriptions
Pin Description
Inputs
R
IN
Analog Input for Red Channel.
G
IN
Analog Input for Green Channel.
B
B
IN
Analog Input for Blue Channel. High impedance inputs that accept the red, green, and blue channel graphics
signals, respectively. (The three channels are identical, and can be used for any colors, but colors are assigned for
convenient reference.) They accommodate input signals ranging from 0.5 V to 1.0 V full scale. Signals should be
ac-coupled to these pins to support clamp operation.
HSYNC
Horizontal Sync Input. This input receives a logic signal that establishes the horizontal timing reference and
provides the frequency reference for pixel clock generation. The logic sense of this pin is controlled by serial
Register 0x0E, Bit 6 (Hsync polarity). Only the leading edge of Hsync is active; the trailing edge is ignored. When
Hsync polarity = 0, the falling edge of Hsync is used. When Hsync polarity = 1, the rising edge is active. The input
includes a Schmitt trigger for noise immunity, with a nominal input threshold of 1.5 V.
VSYNC
Vertical Sync Input. This is the input for vertical sync.
SOGIN
Sync-on-Green Input. This input is provided to assist with processing signals with embedded sync, typically on the
green channel. The pin is connected to a high speed comparator with an internally generated threshold. The
threshold level can be programmed in 10 mV steps to any voltage between 10 mV and 330 mV above the
negative peak of the input signal. The default voltage threshold is 150 mV. When connected to an ac-coupled
graphics signal with embedded sync, it produces a noninverting digital output on SOGOUT. (This is usually a
composite sync signal, containing both vertical and horizontal sync information that must be separated before
passing the horizontal sync signal to Hsync.) When not used, this input should be left unconnected. For more
details on this function and how it should be configured, refer to the Sync-on-Green section.
CLAMP
External Clamp Input. This logic input can be used to define the time during which the input signal is clamped to
ground. It should be exercised when the reference dc level is known to be present on the analog input channels,
typically during the back porch of the graphics signal. The CLAMP pin is enabled by setting control bit clamp
function to 1, (Register 0x0F, Bit 7, default is 0). When disabled, this pin is ignored and the clamp timing is
determined internally by counting a delay and duration from the trailing edge of the Hsync input. The logic sense
of this pin is controlled by clamp polarity Register 0x0F, Bit 6. When not used, this pin must be grounded and
clamp function programmed to 0.
COAST
Clock Generator Coast Input (Optional). This input can be used to cause the pixel clock generator to stop
synchronizing with Hsync and continue producing a clock at its current frequency and phase. This is useful when
processing signals from sources that fail to produce horizontal sync pulses during the vertical interval. The Coast
signal is generally not required for PC-generated signals. The logic sense of this pin is controlled by Coast polarity
(Register 0x0F, Bit 3). When not used, this pin can be grounded and Coast polarity programmed to 1, or tied high
(to V
D
through a 10 k resistor) and Coast polarity programmed to 0. Coast polarity defaults to 1 at power-up.
Outputs
HSOUT
Horizontal Sync Output. A reconstructed and phase-aligned version of the Hsync input. Both the polarity and
duration of this output can be programmed via serial bus registers. By maintaining alignment with DATACK and
Data outputs, data timing with respect to horizontal sync can always be determined.
VSOUT
Vertical Sync Output. A reconstructed and phase-aligned version of the video Vsync. The polarity of this output
can be controlled via a serial bus bit. The placement and duration in all modes is set by the graphics transmitter.
SOGOUT
Sync-on-Green Slicer Output. This pin outputs either the signal from the sync-on-green slicer comparator or an
unprocessed but delayed version of the Hsync input. See the sync processing block diagram (Figure 14) to view
how this pin is connected. (Apart from slicing off SOG, the output from this pin gets no other additional process-
ing on the AD9985A. Vsync separation is performed via the sync separator.)
AD9985A
Rev. 0 | Page 10 of 32
Pin Description
Data Outputs
RED
Data Output, Red Channel.
GREEN
Data Output, Green Channel.
BLUE
Data Output, Blue Channel. The main data outputs. Bit 7 is the MSB. The delay from pixel sampling time to output
is fixed. When the sampling time is changed by adjusting the phase register, the output timing is shifted as well.
The DATACK and HSOUT outputs are also moved, so the timing relationship among the signals is maintained. For
exact timing information, refer to Figure 9, Figure 10, and Figure 11.
Data Clock Output
DATACK
Data Output Clock. This is the main clock output signal used to strobe the output data and HSOUT into external
logic. It is produced by the internal clock generator and is synchronous with the internal pixel sampling clock.
When the sampling time is changed by adjusting the phase register, the output timing is shifted as well. The Data,
DATACK, and HSOUT outputs are all moved, so the timing relationship among the signals is maintained.
References
REF BYPASS
Internal Reference Bypass. Bypass for the internal 1.25 V band gap reference. It should be connected to ground
through a 0.1 F capacitor. The absolute accuracy of this reference is 4%, and the temperature coefficient is 50
ppm, which is adequate for most AD9985A applications. If higher accuracy is required, an external reference can
be used instead.
MIDSCV
Midscale Voltage Reference Bypass. Bypass for the internal midscale voltage reference. It should be connected to
ground through a 0.1 F capacitor. The exact voltage varies with the gain setting of the blue channel.
FILT
External Filter Connection. For proper operation, the pixel clock generator PLL requires an external filter. Connect
the filter shown in Figure 6 to this pin. For optimal performance, minimize noise and parasitics on this node.
Power Supply
V
D
Main Power Supply. These pins supply power to the main elements of the circuit. They should be filtered and kept
as quiet as possible.
V
DD
Digital Output Power Supply. A large number of output pins (up to 25) switching at high speed (up to 110 MHz)
generates a lot of power supply transients (noise). These supply pins are identified separately from the V
D
pins so
special care can be taken to minimize output noise transferred into the sensitive analog circuitry. If the AD9985A
is interfacing with lower voltage logic, V
DD
can be connected to a lower supply voltage (as low as 2.5 V) for
compatibility.
PV
D
Clock Generator Power Supply. The most sensitive portion of the AD9985A is the clock generation circuitry. These
pins provide power to the clock PLL and help the user design for optimal performance. The designer should
provide quiet, noise-free power to these pins.
GND
Ground. The ground return for all circuitry on-chip. It is recommended that the AD9985A be assembled on a
single solid ground plane, with careful attention given to ground current paths.
Serial Port (2-Wire)
SDA
Serial Port Data I/O.
SCL
Serial Port Data Clock.
A0
Serial Port Address Input 1. For a full description of the 2-wire serial register and how it works, refer to the 2-Wire
Serial Control Port section.
AD9985A
Rev. 0 | Page 11 of 32
DESIGN GUIDE
GENERAL DESCRIPTION
The AD9985A is a fully integrated solution for capturing analog
RGB signals and digitizing them for display on flat panel moni-
tors or projectors. The circuit is ideal for providing a computer
interface for HDTV monitors or as the front end to high
performance video scan converters. Implemented in a high
performance CMOS process, the interface can capture signals
with pixel rates up to 110 MHz.
The AD9985A includes all necessary input buffering, signal dc
restoration (clamping), offset and gain (brightness and contrast)
adjustment, pixel clock generation, sampling phase control, and
output data formatting. All controls are programmable via a
2-wire serial interface. Full integration of these sensitive analog
functions makes system design straightforward and less
sensitive to the physical and electrical environment.
With a typical power dissipation of only 500 mW and an
operating temperature range of 0C to 70C (-40C to +85C
for the AD9985ABST), the device requires no special
environmental considerations.
DIGITAL INPUTS
All digital inputs on the AD9985A operate to 3.3 V CMOS
levels. However, all digital inputs are 5 V tolerant. Applying 5 V
to them does not cause any damage.
INPUT SIGNAL HANDLING
The AD9985A has one high impedance analog input pin for
each of the red, green, and blue channels. They accommodate
signals ranging from 0.5 V to 1.0 V p-p.
Signals are typically brought onto the interface board via a
DVI-I connector, a 15-pin D connector, or via BNC connectors.
The AD9985A should be located as close as practical to the
input connector. Signals should be routed via matched-
impedance traces (normally 75 ) to the IC input pins.
At this point, the signal should be resistively terminated (75
to the signal ground return) and capacitively coupled to the
AD9985A inputs through 47 nF capacitors. These capacitors
form part of the dc restoration circuit.
When impedances are perfectly matched, the best performance
can be obtained with the widest possible signal bandwidth. The
ultrawide bandwidth inputs of the AD9985A (300 MHz) can
track the input signal continuously as it moves from one pixel
level to the next, and digitize the pixel during a long, flat pixel
time. In many systems, however, there are mismatches,
reflections, and noise, which can result in excessive ringing and
distortion of the input waveform. This makes it more difficult
to establish a sampling phase that provides good image quality.
It has been shown that a small inductor in series with the input
is effective in rolling off the input bandwidth slightly and
providing a high quality signal over a wider range of conditions.
Using a Fair-Rite #2508051217Z0 High Speed Signal Chip Bead
inductor in the circuit of Figure 3 yields good results in most
applications.
RGB
INPUT
R
IN
G
IN
B
IN
47nF
75
05484-003
Figure 3. Analog Input Interface Circuit
HSYNC, VSYNC INPUTS
The interface also takes a horizontal sync signal, which is used
to generate the pixel clock and clamp timing. This can be either
a sync signal directly from the graphics source, or a preproc-
essed TTL or CMOS level signal.
The Hsync input includes a Schmitt trigger buffer for immunity
to noise and signals with long rise times. In typical PC-based
graphic systems, the sync signals are simply TTL-level drivers
feeding unshielded wires in the monitor cable. As such, no
termination is required.
SERIAL CONTROL PORT
The serial control port is designed for 3.3 V logic. If there are
5 V drivers on the bus, these pins should be protected with
150 series resistors placed between the pull-up resistors and
the input pins.
OUTPUT SIGNAL HANDLING
The digital outputs are designed and specified to operate from a
3.3 V power supply (V
DD
). They can also work with a V
DD
as low
as 2.5 V for compatibility with other 2.5 V logic.
CLAMPING
RGB Clamping
To properly digitize the incoming signal, the dc offset of the
input must be adjusted to fit the range of the on-board ADCs.
Most graphics systems produce RGB signals with black at
ground and white at approximately 0.75 V. However, if sync
signals are embedded in the graphics, the sync tip is often at
ground, black is at 300 mV, and white is at approximately 1.0 V.
Some common RGB line amplifier boxes use emitter-follower
buffers to split signals and increase drive capability. This
introduces a 700 mV dc offset to the signal, which must be
removed for proper capture by the AD9985A.
The key to clamping is to identify a portion (time) of the signal
when the graphic system is known to be producing black. An
offset is then introduced that results in the ADCs producing a
AD9985A
Rev. 0 | Page 12 of 32
black output (code 0x00) when the known black input is
present. The offset then remains in place when other signal
levels are processed, and the entire signal is shifted to eliminate
offset errors.
In most PC graphics systems, black is transmitted between
active video lines. With CRT displays, when the electron beam
has completed writing a horizontal line on the screen (at the
right side), the beam is deflected quickly to the left side of the
screen (called horizontal retrace), and a black signal is provided
to prevent the beam from disturbing the image.
In systems with embedded sync, a blacker-than-black signal
(Hsync) is produced briefly to signal the CRT that it is time to
begin a retrace. For obvious reasons, it is important to avoid
clamping on the tip of Hsync. Fortunately, there is virtually
always a period following Hsync, called the back porch, when a
good black reference is provided. This is the time when clamp-
ing should be performed.
The clamp timing can be established by simply exercising the
CLAMP pin at the appropriate time (with External Clamp = 1).
The polarity of this signal is set by the clamp polarity bit.
A simpler method of clamp timing uses the AD9985A internal
clamp timing generator. The clamp placement register is pro-
grammed with the number of pixel times that should pass after
the trailing edge of Hsync before clamping starts. A second
register (clamp duration) sets the duration of the clamp. These
are both 8-bit values, which provide considerable flexibility in
clamp generation. The clamp timing is referenced to the trailing
edge of Hsync because, though Hsync duration can vary widely,
the back porch (black reference) always follows Hsync. A good
starting point for establishing clamping is to set the clamp
placement to 0x09 (providing 9 pixel periods for the graphics
signal to stabilize after sync) and set the clamp duration to 0x14
(giving the clamp 20 pixel periods to re-establish the black
reference).
Clamping is accomplished by placing an appropriate charge on
the external input coupling capacitor. The value of this
capacitor affects the performance of the clamp. If it is too small,
there is a significant amplitude change during a horizontal line
time (between clamping intervals). If the capacitor is too large,
it takes excessively long for the clamp to recover from a large
change in incoming signal offset. The recommended value
(47 nF) results in recovering from a step error of 100 mV to
within 1/2 LSB in 10 lines with a clamp duration of 20 pixel
periods on a 60 Hz SXGA signal.
YUV Clamping
YUV graphics signals are slightly different from RGB signals, as
the dc reference level (black level in RGB signals) can be at the
midpoint of the graphics signal rather than at the bottom. For
these signals, it might be necessary to clamp to the midscale
range of the ADC range (0x80) rather than at the bottom of the
ADC converter range (0x00).
Clamping to midscale rather than to ground can be accom-
plished by setting the clamp select bits in the serial bus register.
Each of the three converters has its own selection bit so that
they can be clamped to either midscale or ground independ-
ently. These bits are located in Register 0x10, Bits [2:0]. The
midscale reference voltage that each ADC clamps to is provided
on the MIDSCV pin (Pin 37). This pin should be bypassed to
ground with a 0.1 F capacitor, even if midscale clamping is not
required.
GAIN AND OFFSET CONTROL
The AD9985A can accommodate input signals with inputs
ranging from 0.5 V to 1.0 V full scale. The full-scale range is set
in three 8-bit registers (red gain, green gain, and blue gain).
Note that increasing the gain setting results in an image with
less contrast.
The offset control shifts the entire input range, resulting in a
change in image brightness. Three 7-bit registers (red offset,
green offset, blue offset) provide independent settings for each
channel. The offset controls provide a 63 LSB adjustment
range. This range is connected with the full-scale range, so if the
input range is doubled (from 0.5 V to 1.0 V), the offset step size
is also doubled (from 2 mV per step to 4 mV per step).
Figure 4 shows the interaction of gain and offset controls. The
magnitude of an LSB in offset adjustment is proportional to the
full-scale range, so changing the full-scale range also changes
the offset. The change is minimal if the offset setting is near
midscale. When changing the offset, the full-scale range is not
affected, but the full-scale level is shifted by the same amount as
the zero-scale level.
GAIN
1.0
0
00H
FFH
INPUT RANGE (V)
0.5
OFFSET = 00H
OFFSET = 3FH
OFFSET = 7FH
OFFSET = 00H
OFFSET = 7FH
OFFSET = 3FH
05484-004
Figure 4. Gain and Offset Control
Auto Offset
In addition to the manual offset adjustment mode (via registers
0x0B to 0x0D), the AD9985A also includes circuitry to auto-
matically calibrate the offset for each channel. By monitoring
AD9985A
Rev. 0 | Page 13 of 32
the output of each ADC during the back porch of the input
signals, the AD9985A can self-adjust to eliminate any offset
errors in its own ADC channels, as well as any offset errors
present on the incoming graphics or video signals.
To activate the auto offset mode, set Register 0x1D, Bit 7 to 1.
Next, the target code registers (0x19 through 0x1B) must be
programmed. The values programmed into the target code
registers should be the output code desired from the AD9985A
during the back porch reference time. For example, for RGB
signals, all three registers are normally programmed to code 1,
while for YPbPr signals, the green (Y) channel is normally
programmed to code 1, and the blue and red channels (Pb and
Pr) are normally set to 128. Any target code value between 1
and 254 can be set, although the AD9985A's offset range may
not be able to reach every value. Intended target code values
range from (but are not limited to) 1 to 40 when ground
clamping, and 90 to 170 when midscale clamping.
The ability to program a target code for each channel gives
users a large degree of freedom and flexibility. While in most
cases all channels are set either to 1 or 128, the flexibility to
select other values allows the possibility of inserting intentional
skews between channels. It also allows the ADC range to be
skewed so that voltages outside of the normal range can be
digitized. For example, setting the target code to 40 allows the
sync tip, which is normally below black level, to be digitized and
evaluated.
Lastly, when in auto offset mode, the manual offset registers
(0x0B to 0x0D) have new functionality. The values in these
registers are digitally added to the value of the ADC output. The
purpose of doing this is to match a benefit that is present with
manual offset adjustment. Adjusting these registers is an easy
way to make brightness adjustments. Although some signal
range is lost with this method, it has proven to be a very
popular function. In order to be able to increase and decrease
brightness, the values in these registers in this mode are signed
twos complement. The digital adder is only used in auto offset
mode. Although it cannot be disabled, setting the offset
registers to all 0s effectively disables it by always adding 0.
SYNC-ON-GREEN
The sync-on-green input operates in two steps. First, it sets a
baseline clamp level off of the incoming video signal with a
negative peak detector. Second, it sets the sync trigger level to a
programmable level (typically 150 mV) above the negative
peak. The sync-on-green input must be ac-coupled to the green
analog input through its own capacitor, as shown in Figure 5.
The value of the capacitor must be 1 nF 20%. If sync-on-green
is not used, this connection is not required. The sync-on-green
signal is always negative polarity.
R
IN
B
IN
G
IN
SOG
47nF
47nF
47nF
1nF
05484-005
Figure 5. Typical Clamp Configuration
CLOCK GENERATION
A phase-locked loop (PLL) is used to generate the pixel clock.
In this PLL, the Hsync input provides a reference frequency. A
voltage controlled oscillator (VCO) generates a much higher
pixel clock frequency. This pixel clock is divided by the PLL
divide value (Register 0x01 and Register 0x02) and phase
compared with the Hsync input. Any error is used to shift the
VCO frequency and maintain lock between the two signals.
The stability of this clock is a very important element in provid-
ing the clearest and most stable image. During each pixel time,
there is a period during which the signal is slewing from the old
pixel amplitude and settling at its new value. Then, there is a
time when the input voltage is stable before the signal must slew
to a new value (Figure 6). The ratio of the slewing time to the
stable time is a function of the bandwidth of the graphics DAC
and the bandwidth of the transmission system (cable and
termination). It is also a function of the overall pixel rate.
Clearly, if the dynamic characteristics of the system remain
fixed, the slewing and settling time is, likewise, fixed. This time
must be subtracted from the total pixel period, leaving the
stable period. At higher pixel frequencies, the total cycle time is
shorter, and the stable pixel time also becomes shorter.
PIXEL CLOCK
INVALID SAMPLE TIMES
05484-006
Figure 6. Pixel Sampling Times
Any jitter in the clock reduces the precision with which the
sampling time can be determined, and must also be subtracted
from the stable pixel time.
Considerable care has been taken in the design of the
AD9985A's clock generation circuit to minimize jitter. As shown
in Figure 7, the clock jitter of the AD9985A is less than 5% of
the total pixel time in all operating modes, making the
reduction in the valid sampling time negligible due to jitter.
AD9985A
Rev. 0 | Page 14 of 32
FREQUENCY (MHz)
14
12
0
0
P
I
X
E
L CLOCK J
I
TTE
R (p-p) (%)
10
8
6
4
2
10 20 30 40 50 60 70 80 90 100 110 120 130 140 150
05484-007
Figure 7. Pixel Clock Jitter vs. Frequency
The PLL characteristics are determined by the loop filter design,
the PLL charge pump current, and the VCO range setting. The
loop filter design is shown in Figure 8. Recommended settings
of VCO range and charge pump current for VESA standard
display modes are listed in Table 9.
C
P
0.0082
F
C
Z
0.082
F
R
Z
2.7k
FILT
PV
D
05484-008
Figure 8. PLL Loop Filter Detail
Four programmable registers are provided to optimize the
performance of the PLL.
12-Bit Divisor Register
The input Hsync frequencies range from 15 kHz to 110 kHz.
The PLL multiplies the frequency of the Hsync signal,
producing pixel clock frequencies in the range of 12 MHz to
110 MHz. The divisor register controls the exact multiplication
factor. This register can be set to any value between 221 and
4095. (The divide ratio that is actually used is the programmed
divide ratio plus 1.)
2-Bit VCO Range Register
To improve the noise performance of the AD9985A, the VCO
operating frequency range is divided into three overlapping
regions. The VCO range register sets this operating range.
Table 6 shows the frequency ranges for the lowest and highest
regions.
Table 6. VCO Frequency Ranges
Pixel Clock Range (MHz)
PV1 PV0 AD9985AKSTZ
AD9985ABSTZ
0
0
12 to 32
12 to 30
0
1
32 to 64
30 to 60
1
0
64 to 110
60 to 110
1
1
110 to 140
3-Bit Charge Pump Current Register
This register allows the current that drives the low-pass loop filter
to be varied. The possible current values are listed in Table 7.
Table 7. Charge Pump Current/Control Bits
Ip2 Ip1 Ip0 Current
(A)
0 0 0 50
0 0 1 100
0 1 0 150
0 1 1 250
1 0 0
350
1 0 1 500
1 1 0 750
1 1 1 1500
5-Bit Phase Adjust Register
The phase of the generated sampling clock can be shifted to
locate an optimum sampling point within a clock cycle. The
phase adjust register provides 32 phase-shift steps of 11.25
each. The Hsync signal with an identical phase shift is available
through the HSOUT pin.
The COAST pin is used to allow the PLL to continue to run at
the same frequency in the absence of the incoming Hsync signal
or during disturbances in Hsync (such as equalization pulses).
This can be used during the vertical sync period, or any other
time that the Hsync signal is unavailable. The polarity of the
Coast signal is set through the Coast polarity register. Also, the
polarity of the Hsync signal is set through the Hsync polarity
register. If not using automatic polarity detection, the Hsync
and Coast polarity bits should be set to match the respective
polarities of the input signals.
POWER MANAGEMENT
The AD9985A uses the activity detect circuits, the active
interface bits in the serial bus, the active interface override bits,
and the power-down bit to determine the correct power state.
The three power states are full-power, seek mode, and power-
down. Table 8 summarizes how the AD9985A determines
which power mode to be in and which circuitry is powered
on/off in each of these modes. The power-down command has
priority over the automatic circuitry.
Table 8. Power-Down Mode Descriptions
Mode
Inputs
Power-Down
1
Sync
Detect
2
Powered On or
Comments
Full-
Power
1 1
Everything
Seek
Mode
1
0
Serial Bus, Sync Activity
Detect, SOG, Band Gap
Reference
Power-
Down
0
X
Serial Bus, Sync Activity
Detect, SOG, Band Gap
Reference
1
Power-down is controlled via Bit 1 in Serial Bus Register 0x0F.
2
Sync detect is determined by OR'ing Bits 7, 4, and 1 in Serial Bus Register 0x14.
AD9985A
Rev. 0 | Page 15 of 32
Table 9. Recommended VCO Range and Charge Pump Current Settings for Standard Display Formats
Standard
Modes Resolution
Refresh
Rate
Horizontal
Frequency
Pixel Rate
PLL Div
AD9985AKSTZ
VCORNGE Current
AD9985ABSTZ
VCORNGE Current
VGA
640 480
60 Hz
31.5 kHz
25.175 MHz
799
00
110
00
011
72 Hz
37.7 kHz
31.500 MHz
835
00
110
01
010
75 Hz
37.5 kHz
31.500 MHz
841
00
110
01
010
85 Hz
43.3 kHz
36.000 MHz
831
01
100
01
010
SVGA
800 600
56 Hz
35.1 kHz
36.000 MHz
1025
01
100
01
010
60 Hz
37.9 kHz
40.000 MHz
1055
01
100
01
011
72 Hz
48.1 kHz
50.000 MHz
1039
01
101
01
100
75 Hz
46.9 kHz
49.500 MHz
1055
01
101
01
100
85 Hz
53.7 kHz
56.250 MHz
1047
01
101
01
101
XGA
1024 768
60 Hz
48.4 kHz
65.000 MHz
1343
10
101
10
011
70 Hz
56.5 kHz
75.000 MHz
1327
10
100
10
011
75 Hz
60.0 kHz
78.750 MHz
1313
10
100
10
011
80 Hz
64.0 kHz
85.500 MHz
1335
10
101
10
100
85 Hz
68.3 kHz
94.500 MHz
1383
10
101
10
100
SXGA
1280 1024
60 Hz
64.0 kHz
108.000 MHz
1687
10
110
10
101
75 Hz
80.0 kHz
135.000 MHz
1687
11
110
TV Modes
480i
720 480
60Hz
15.75 kHz
13.51MHz
857
00
011
00
011
480p
720 483
60Hz
31.47 kHz
27.00 MHz
857
00
110
00
011
720p
1280 720
60Hz
45.0 kHz
74.25 MHz
1649
10
100
10
011
1080i
1920 1080
60Hz
33.75 kHz
74.25 MHz
2199
10
100
10
011
TIMING
The timing diagrams in this section show the operation of the
AD9985A.
The output data clock signal is created so that its rising edge
always occurs between data transitions, and can be used to latch
the output data externally.
The pipeline in the AD9985A must be flushed before valid data
becomes available. This means that four data sets are presented
before valid data is available.
t
PER
t
CYCLE
t
SKEW
DATACK
DATA
HSOUT
05484-
009
Figure 9. Output Timing
Hsync TIMING
Hsync is processed in the AD9985A to eliminate ambiguity in
the timing of the leading edge with respect to the phase-delayed
pixel clock and data.
The Hsync input is used as a reference to generate the pixel
sampling clock. The sampling phase can be adjusted, with
respect to Hsync, through a full 360 in 32 steps via the phase
adjust register (to optimize the pixel sampling time). Display
systems use Hsync to align memory and display write cycles;
therefore, it is important to have a stable timing relationship
between Hsync output (HSOUT) and data clock (DATACK).
Three things happen to Horizontal Sync in the AD9985A. First,
the polarity of Hsync input is determined and thus has a known
output polarity. The known output polarity can be programmed
either active high or active low (Register 0x0E,
Bit 5). Second, HSOUT is aligned with DATACK and data
outputs. Third, the duration of HSOUT (in pixel clocks) is set
via Register 0x07. HSOUT is the sync signal that should be used
to drive the rest of the display system.
AD9985A
Rev. 0 | Page 16 of 32
COAST TIMING
In most computer systems, the Hsync signal is provided
continuously on a dedicated wire. In these systems, the Coast
input and function are unnecessary and should not be used, and
the pin should be permanently connected to the inactive state.
In some systems, however, Hsync is disturbed during the
vertical sync period (Vsync). In some cases, Hsync pulses
disappear. In other systems, such as those that use composite
sync (Csync) signals or embedded sync-on-green (SOG), Hsync
includes equalization pulses or other distortions during Vsync.
To avoid upsetting the clock generator during Vsync, it is
important to ignore these distortions. If the pixel clock PLL
detects extraneous pulses, it attempts to lock to this new
frequency, and changes frequency by the end of the Vsync
period. It then takes a few lines of correct Hsync timing to
recover at the beginning of a new frame, resulting in a tearing of
the image at the top of the display.
The Coast input is provided to eliminate this problem. It is an
asynchronous input that disables the PLL input and allows the
clock to free-run at its then-current frequency. The PLL can
free-run for several lines without significant frequency drift.
.
P0
P1
P2
P3
P4
P5
P6
P7
5-PIPE DELAY
D0
D1
D2
D3
D4
D5
D6
D7
RGB
IN
HSYNC
PxCK
HS
ADCCK
DATACK
D
OUTA
HSOUT
VARIABLE DURATION
05484-010
Figure 10. 4:4:4 Mode (For RGB and YUV)
P0
P1
P2
P3
P4
P5
P6
P7
5-PIPE DELAY
Y0
Y1
Y2
Y3
Y4
Y5
Y6
Y7
RGB
IN
HSYNC
PxCK
HS
ADCCK
DATACK
G
OUTA
HSOUT
U0
V1
U2
V3
U4
V5
U6
V7
R
OUTA
VARIABLE DURATION
05484-011
Figure 11. 4:2:2 Mode (For YUV Only)
AD9985A
Rev. 0 | Page 17 of 32
2-WIRE SERIAL REGISTER MAP
The AD9985A is initialized and controlled by a set of registers that determine the operating modes. An external controller is used to write
and read the control registers through the two-line serial interface port.
Table 10. Control Register Map
Hexadecimal
Address
Write and
Read or
Read-Only
Bits
Default
Value
Register
Name
Function
0x00
RO
7:0
Chip Revision
An 8-bit register that represents the silicon revision level.
0x01
1
R/W
7:0
01101001
PLL Div MSB
This register is for Bits [11:4] of the PLL divider. Greater values mean
the PLL operates at a faster rate. This register should be loaded first
whenever a change is needed. This will give the PLL more time to lock.
0x02
1
R/W
7:4
1101****
PLL Div LSB
Bits [7:4] of this word are written to the LSBs [3:0] of the PLL divider
word.
0x03
R/W
7:3 01******
Bits [7:6] VCO Range. Selects VCO frequency range. (See the PLL
description.)
**001***
Bits [5:3] Charge Pump Current. Varies the current that drives the
low-pass filter. (See the PLL description.)
0x04
R/W
7:3 10000*** Phase
Adjust ADC Clock Phase Adjustment. Larger values mean more delay.
(1 LSB = T/32)
0x05
R/W
7:0 10000000 Clamp
Placement
Places the clamp signal an integer number of clock periods after the
trailing edge of the Hsync signal.
0x06
R/W
7:0 10000000 Clamp
Duration
Number of clock periods that the clamp signal is actively clamping.
0x07
R/W
7:0 00100000 Hsync Output
Pulse Width
Sets the number of pixel clocks that HSOUT will remain active.
0x08 R/W
7:0
10000000
Red
Gain
0x09 R/W
7:0
10000000
Green
Gain
0x0A R/W 7:0
10000000
Blue
Gain
Controls the ADC input range (contrast) of each respective channel.
Greater values give less contrast.
0x0B R/W
7:1
1000000*
Red
Offset
0x0C R/W 7:1
1000000*
Green
Offset
0x0D R/W 7:1
1000000*
Blue
Offset
Controls dc offset (brightness) of each respective channel. Greater
values decrease brightness.
0x0E
R/W
7:0 0******* Sync
Control Bit 7--Hsync Polarity Override. (Logic 0 = polarity determined by
chip, Logic 1 = polarity set by Bit 6 in Register 0x0E.)
*1******
Bit 6--Hsync Input Polarity. Indicates polarity of incoming Hsync
signal to the PLL. (Logic 0 = active low, Logic 1 = active high.)
**0*****
Bit 5--Hsync Output Polarity. (Logic 0 = logic high sync,
Logic 1 = logic low sync.)
***0****
Bit 4--Active Hsync Override. If set to Logic 1, the user can select the
Hsync to be used via Bit 3. If set to Logic 0, the active interface is
selected via Bit 6 in Register 0x14.
****0***
Bit 3--Active Hsync Select. Logic 0 selects Hsync as the active sync.
Logic 1 selects sync-on-green as the active sync. Note that the
indicated Hsync is used only if Bit 4 is set to Logic 1 or if both syncs
are active. (Bits 1, 7 = Logic 1 in Register 0x14.)
*****0**
Bit 2--Vsync Output Invert. (Logic 1 = no invert, Logic 0 = invert.)
******0*
Bit 1--Active Vsync Override. If set to Logic 1, the user can select the
Vsync to be used via Bit 0. If set to Logic 0, the active interface is
selected via Bit 3 in Register 0x14.
*******0
Bit 0--Active Vsync Select. Logic 0 selects raw Vsync as the output
Vsync. Logic 1 selects sync separated Vsync as the output Vsync.
Note that the indicated Vsync is used only if Bit 1 is set to Logic 1.
0x0F R/W
7:1
0*******
Bit 7--Clamp Function. Chooses between Hsync for clamp signal or
another external signal to be used for clamping. (Logic 0 = Hsync,
Logic 1 = Clamp.)
AD9985A
Rev. 0 | Page 18 of 32
Hexadecimal
Address
Write and
Read or
Read-Only Bits
Default
Value
Register
Name Function
*1******
Bit 6--Clamp Polarity. Valid only with external clamp signal.
(Logic 0 = active high, Logic 1 selects active low.)
**0*****
Bit 5--Coast Select. Logic 0 selects the COAST input pins to be used
for the PLL coast. Logic 1 selects Vsync to be used for the PLL coast.
***0****
Bit 4--Coast Polarity Override. (Logic 0 = polarity determined by
chip, Logic 1 = polarity set by Bit 3 in Register 0x0F.)
****1***
Bit 3--Coast Polarity. Selects polarity of external Coast signal
(Logic 0 = active low, Logic 1 = active high).
*****1**
Bit 2--Seek Mode Override (Logic 1 = allow low power mode,
Logic 0 = disallow low power mode).
******1*
Bit 1--PWRDN. Full Chip Power-Down, Active Low (Logic 0 = full chip
power-down, Logic 1 = normal).
0x10 R/W
7:3
10111***
Sync-on-Green
Threshold
Sync-on-Green Threshold. Sets the voltage level of the sync-on-
green slicer's comparator.
*****0**
Bit 2--Red Clamp Select. Logic 0 selects clamp to ground. Logic 1
selects clamp to midscale (voltage at Pin 37).
******0*
Bit 1--Green Clamp Select. Logic 0 selects clamp to ground. Logic 1
selects clamp to midscale (voltage at Pin 37).
*******0
Bit 0-- Blue Clamp Select. Logic 0 selects clamp to ground. Logic 1
selects clamp to midscale (voltage at Pin 37).
0x11 R/W
7:0
00100000
Sync Separator
Threshold
Sync Separator Threshold. Sets the number of internal 5 MHz clock
periods the sync separator counts to before toggling high or low.
This should be set to some number greater than the maximum Hsync
or equalization pulse width.
0x12 R/W
7:0
00000000
Pre-Coast
Pre-Coast. Sets the number of Hsync periods that Coast becomes
active prior to Vsync.
0x13 R/W
7:0
00000000
Post-Coast
Post-Coast. Sets the number of Hsync periods that Coast stays active
following Vsync.
0x14 RO 7:0
Sync
Detect
Bit 7--Hsync detect. It is set to Logic 1 if Hsync is present on the
analog interface; otherwise it is set to Logic 0.
Bit 6--AHS: Active Hsync. This bit indicates which analog Hsync is
being used (Logic 0 = Hsync input pin, Logic 1 = Hsync from
sync-on-green).
Bit 5--Input Hsync Polarity Detect (Logic 0 = active low,
Logic 1 = active high).
Bit 4--Vsync Detect. It is set to Logic 1 if Vsync is present on the
analog interface; otherwise it is set to Logic 0.
Bit 3--AVS: Active Vsync. This bit indicates which analog Vsync is
being used (Logic 0 = Vsync input pin, Logic 1 = Vsync from
sync separator).
Bit 2--Output Vsync Polarity Detect (Logic 0 = active low,
Logic 1 = active high).
Bit 1--Sync-on-Green Detect. It is set to Logic 1 if sync is present on
the green video input; otherwise it is set to 0.
Bit 0--Input Coast Polarity Detect (Logic 0 = active low,
Logic 1 = active high).
0x15
R/W
7:2 111111** Reserved
Bits [7:2] Reserved for future use. Must be written to 111111 for
proper operation.
1
******1*
Output
Formats
Bit 1--4:2:2 Output Formatting Mode (Logic 0 = 4:2:2 mode,
Logic 1= 4:4:4 mode).
0
*******1
Reserved
Bit 0--Must be set to 0 for proper operation.
AD9985A
Rev. 0 | Page 19 of 32
Hexadecimal
Address
Write and
Read or
Read-Only Bits
Default
Value
Register
Name Function
0x16
R/W
7 0******* Extra PLL
Divider
Bit 7--Extra PLL Divider. (Logic 0 = off, Logic 1 = extra divide-by-2).
6:5
*00*****
SOGIN
Bandwidth
Control
Bits [6:5]--SOGIN Bandwidth Control; 00 = 300 MHz;
01 or 10 = 13 MHz; 11 = 6.5 MHz.
4
***0****
Analog Input
Bandwidth
Control
Bit 4--Sets the bandwdith of the red, green and blue analog inputs.
(Logic 0 = 300 MHz, Logic 1 = 7 MHz).
3:0
****0000
Reserved
Reserved.
0x17 RO 7:0
Test
Register
Reserved.
0x18 RO 7:0
Test
Register
Reserved.
0x19
R/W
7:0 00000100 Red Target
Code
Target Code for Auto-Offset Operation.
0x1A
R/W
7:0 00000100 Green Target
Code
Target Code for Auto-Offset Operation.
0x1B
R/W
7:0 00000100 Blue Target
Code
Target Code for Auto-Offset Operation.
0x1C
R/W
7:0
00010001
Reserved
Must be written to 0x11 for proper operation.
0x1D
R/W
7 0******* Auto Offset
Enable
Enables the auto-offset circuitry.
6
*0******
Hold Auto
Offset
Holds the offset output of the auto-offset at the current value.
5:2
**1001**
Reserved
Must be written to 9 for proper operation.
1:0
******10
Update Mode
Changes the update rate of the auto-offset.
0x1E
R/W
7:0
0000****
Test Register
Must be set to default value.
1
The AD9985A only updates the PLL divide ratio when the LSBs are written to (Register 0x02).
2-WIRE SERIAL CONTROL REGISTER DETAIL CHIP
IDENTIFICATION
00 70
Chip
Revision
An 8-bit register that represents the silicon revision.
PLL DIVIDER CONTROL
01
70
PLL Divide Ratio MSBs
The 8 most significant bits of the 12-bit PLL divide
ratio PLLDIV. (The operational divide ratio is
PLLDIV + 1.)
The PLL derives a master clock from an incoming
Hsync signal. The master clock frequency is then
divided by an integer value, such that the output is
phase-locked to Hsync. This PLLDIV value
determines the number of pixel times (pixels plus
horizontal blanking overhead) per line. This is
typically 20% to 30% more than the number of active
pixels in the display.
The 12-bit value of the PLL divider supports divide
ratios from 2 to 4095. The higher the value loaded in
this register, the higher the resulting clock frequency
with respect to a fixed Hsync frequency.
VESA has established some standard timing
specifications that assist in determining the value for
PLLDIV as a function of horizontal and vertical
display resolution and frame rate (Table 8).
However, many computer systems do not conform
precisely to the recommendations, and these numbers
should be used only as a guide. The display system
manufacturer should provide automatic or manual
means for optimizing PLLDIV. An incorrectly set
PLLDIV usually produces one or more vertical noise
bars on the display. The greater the error, the greater
the number of bars produced.
The power-up default value of PLLDIV is 1693
(PLLDIVM = 0x69, PLLDIVL = 0xDx).
The AD9985A updates the full-divide ratio only when
the LSBs are changed. Writing to the MSB by itself
does not trigger an update.
02
74 PLL Divide Ratio LSBs
The 4 least significant bits of the 12-bit PLL divide
ratio PLLDIV. The operational divide ratio is
PLLDIV + 1.
AD9985A
Rev. 0 | Page 20 of 32
The power-up default value of PLLDIV is 1693
(PLLDIVM = 0x69, PLLDIVL = 0xDx). The
AD9985A updates the full divide ratio only when this
register is written to.
CLOCK GENERATOR CONTROL
03
76
VCO Range Select
Two bits that establish the operating range of the clock
generator.
VCORNGE must be set to correspond with the
desired operating frequency (incoming pixel rate).
The PLL gives the best jitter performance at high
frequencies. For this reason, to output low pixel rates
and still get good jitter performance, the PLL actually
operates at a higher frequency but then divides down
the clock rate afterwards. Table 11 shows the pixel
rates for each VCO range setting. The PLL output
divisor is automatically selected with the VCO range
setting.
Table 11. VCO Ranges
Pixel Clock Range (MHz)
PV1 PV0 AD9985AKSTZ
AD9985ABSTZ
0
0
12 to 32
12 to 30
0 1
32 to 64 (power-up
default)
30 to 60 (power-up
default)
1
0
64 to 110
60 to 110
1
1
110 to 140
03
53
Current Charge Pump Current
Three bits that establish the current driving the loop
filter in the clock generator.
Current must be set to correspond with the desired
operating frequency (incoming pixel rate).
Table 12. Charge Pump Currents
CURRENT Current
(A)
000 50
001
100 (power-up default)
010 150
011 250
100 350
101 500
110 750
111 1500
04
73
Clock Phase Adjust
A 5-bit value that adjusts the sampling phase in 32
steps across one pixel time. Each step represents an
11.25 shift in sampling phase.
The power-up default value is 16.
CLAMP TIMING
05 70
Clamp
Placement
An 8-bit register that sets the position of the internally
generated clamp.
When clamp function (Register 0x0F, Bit 7) = 0, a
clamp signal is generated internally, at a position
established by the clamp placement and for a duration
set by the clamp duration. Clamping is started (clamp
placement) pixel periods after the trailing edge of
Hsync. The clamp placement can be programmed to
any value between 1 and 255.
The clamp should be placed during a time that the
input signal presents a stable black-level reference,
usually the back porch period between Hsync and the
image.
When clamp function = 1, this register is ignored.
06 70
Clamp
Duration
An 8-bit register that sets the duration of the
internally generated clamp.
For the best results, the clamp duration should be set
to include the majority of the black reference signal
time that follows the Hsync signal trailing edge.
Insufficient clamping time can produce brightness
changes at the top of the screen, and a slow recovery
from large changes in the average picture level (APL),
or brightness.
When clamp function = 1, this register is ignored.
HSYNC PULSE WIDTH
07
70
Hsync Output Pulse Width
An 8-bit register that sets the duration of the Hsync
output pulse.
The leading edge of the Hsync output is triggered by
the internally generated, phase-adjusted PLL feedback
clock. The AD9985A then counts a number of pixel
clocks equal to the value in this register. This triggers
the trailing edge of the Hsync output, which is also
phase adjusted.
INPUT GAIN
08
70
Red Channel Gain Adjust (REDGAIN)
An 8-bit word that sets the gain of the red channel.
The AD9985A can accommodate input signals with a
full-scale range of between 0.5 V and 1.0 V p-p.
Setting REDGAIN to 255 corresponds to a 1.0 V input
range. A REDGAIN of 0 establishes a 0.5 V input
range. Increasing REDGAIN results in the picture
having less contrast (the input signal uses fewer of the
available converter codes). See Figure 4.
AD9985A
Rev. 0 | Page 21 of 32
09
70
Green Channel Gain Adjust (GREENGAIN)
An 8-bit word that sets the gain of the green channel.
See REDGAIN (08).
0A
70
Blue Channel Gain Adjust (BLUEGAIN)
An 8-bit word that sets the gain of the blue channel.
See REDGAIN (08).
INPUT OFFSET
0B
71
Red Channel Offset Adjust
This offset register and those that follow have two
modes of operation. One mode is when the auto offset
function is turned off (manual mode) and the other is
when auto offset is turned on.
When in manual offset adjustment mode (auto offset
turned off), this register behaves exactly like the
AD9883A. It is a 7-bit offset binary word that sets the
dc offset of the red channel. One LSB of offset
adjustment equals approximately one LSB change in
the ADC offset. Therefore, the absolute magnitude of
the offset adjustment scales as the gain of the channel
is changed. A nominal setting of 63 results in the
channel nominally clamping the back porch (during
the clamping interval) to Code 00. An offset setting of
127 results in the channel clamping to Code 64 of the
ADC. An offset setting of 0 clamps to Code 63 (off
the bottom of the range). Increasing the value of red
offset decreases the brightness of the channel.
When in auto offset mode, the value in this register is
digitally added to the red channel ADC output. The
purpose of doing this is to match the operation with
manual offset adjustment. Adjusting these registers is
an easy way to make brightness adjustments.
Although some signal range is lost with this method, it
has proven to be a very popular function. In order to
be able to increase and decrease brightness, the values
in these registers in this mode are signed twos comple-
ment (vs. manual mode, where the values in this
register are binary). The digital adder is used only in
auto offset mode. Although it cannot be disabled,
setting this register to all 0s effectively disables it by
always adding 0.
0C
71
Green Channel Offset Adjust
This register works exactly like the Red Channel
Offset Adjust Register (0x0B), except it is for the green
channel.
0D
71
Blue Channel Offset Adjust
This register works exactly like the Red Channel
Offset Adjust register (0x0B), except it is for the blue
channel.
MODE CONTROL 1
0E
7
Hsync Input Polarity Override
This register is used to override the internal circuitry
that determines the polarity of the Hsync signal going
into the PLL.
Table 13. Hsync Input Polarity Override Settings
Override Result
0
Hsync polarity determined by chip
1
Hsync polarity determined by user
The default for Hsync polarity override is 0 (polarity
determined by chip).
0E
6
HSPOL Hsync Input Polarity
A bit that must be set to indicate the polarity of the
Hsync signal that is applied to the PLL Hsync input.
Table 14. Hsync Input Polarity Settings
Polarity Result
0 Active
low
1
Active high (power-up default)
Active low means the leading edge of the Hsync pulse
is negative-going. All timing is based on the leading
edge of Hsync, which is the falling edge. The rising
edge has no effect.
Active high is inverted from the traditional Hsync,
with a positive-going pulse. This means that timing is
based on the leading edge of Hsync, which is now the
rising edge.
The device operates if this bit is set incorrectly, but the
internally generated clamp position, as established by
clamp placement (Register 0x05), is not placed as
expected, which can generate clamping errors.
0E 5
Hsync
Output
Polarity
This bit determines the polarity of the Hsync output
and the SOG output. Table 15 shows the effect of this
option. SYNC indicates the logic state of the sync
pulse.
Table 15. Hsync Output Polarity Settings
Polarity Result
0
Logic 1 (positive polarity; power-up default)
1
Logic 0 (negative polarity)
0E 4 Active
Hsync
Override
This bit is used to override the automatic Hsync
selection. To override, set this bit to Logic 1. When
overriding, the active Hsync is set via Bit 3 in this
register.
AD9985A
Rev. 0 | Page 22 of 32
Table 16. Active Hsync Override Settings
Override Result
0
Autodetermines the active interface (power-up
default)
1
Override, Bit 3 determines the active interface
0E
3
Active Hsync Select
This bit is used under two conditions. It is used to
select the active Hsync when the override bit is set
(Bit 4). Alternately, it is used to determine the active
Hsync when not overriding, but both Hsyncs are
detected.
Table 17. Active Hsync Select Settings
Select Result
0
Hsync input (power-up default)
1 Sync-on-green
input
0E 2 Vsync
Output
Invert
This bit inverts the polarity of the Vsync output
Table 18 shows the effect of this option.
Table 18. Vsync Output Invert Settings
Invert Vsync
Output
0
Invert (power-up default)
1 No
invert
0E
1
Active Vsync Override
This bit is used to override the automatic Vsync
selection. To override, set this bit to Logic 1. When
overriding, the active interface is set via Bit 0 in this
register.
Table 19. Active Vsync Override Settings
Override Result
0
Autodetermines the active Vsync (power-up default)
1
Override, Bit 0 determines the active Vsync
0E
0
Active Vsync Select
This bit is used to select the active Vsync when the
override bit is set (Bit 1).
Table 20. Active Vsync Select Settings
Select Result
0
Vsync input (power-up default)
1 Sync
separator
output
0F
7
Clamp Input Signal Source
This bit determines the source of clamp timing.
Table 21. Clamp Input Signal Source Settings
Clamp Function
Result
0
Internally generated clamp signal (power-
up default)
1
Externally provided clamp signal
A 0 enables the clamp timing circuitry controlled by
clamp placement and clamp duration. The clamp
position and duration is counted from the leading
edge of Hsync.
A 1 enables the external CLAMP input pin. The three
channels are clamped when the clamp signal is active.
The polarity of clamp is determined by the clamp
polarity bit (Register 0x0F, Bit 6).
0F
6
Clamp Input Signal Polarity
This bit determines the polarity of the externally
provided clamp signal.
Table 22. Clamp Input Signal Polarity Settings
Clamp Function
Result
1
Active low (power-up default)
0 Active
high
Logic 1 means that the circuit clamps when CLAMP is
low, and it passes the signal to the ADC when CLAMP
is high.
Logic 0 means that the circuit clamps when CLAMP is
high, and it passes the signal to the ADC when
CLAMP is low.
0F 5 Coast
Select
This bit is used to select the active Coast source. The
choices are the COAST input pin or Vsync. If Vsync is
selected, the additional decision to use the Vsync
input pin or the output from the sync separator needs
to be made (Register 0x0E, Bits 1, 0).
Table 23. Power-Down Settings
Power-Down Result
0
COAST input pin
1
Vsync (See the Coast Select section)
0F
4
Coast Input Polarity Override
This register is used to override the internal circuitry
that determines the polarity of the Coast signal going
into the PLL.
AD9985A
Rev. 0 | Page 23 of 32
Table 24. Coast Input Polarity Override Settings
Override Result
0
Determined by chip (power-up default)
1
Determined by user
0F
3
Coast Input Polarity
This bit indicates the polarity of the Coast signal that
is applied to the PLL COAST input.
Table 25. Coast Input Polarity Settings
Coast Polarity
Result
0 Active
low
1
Active high (power-up default)
Active low means that the clock generator ignores
Hsync inputs when Coast is low, and continues
operating at the same nominal frequency until Coast
goes high.
Active High means that the clock generator ignores
Hsync inputs when Coast is high, and continues
operating at the same nominal frequency until Coast
goes low.
This function needs to be used along with the Coast
polarity override bit (Bit 4).
0F 2 Seek
Mode
Override
This bit is used to either allow or disallow the low
power mode. The low power mode (seek mode)
occurs when there are no signals on any of the Sync
inputs.
Table 26. Seek Mode Override Settings
Override Result
1
Allow seek mode (power-up default)
0
Disallow seek mode
0F 1 PWRDN
This bit is used to put the chip in full power-down. See
the Power Management section for details on which
blocks are powered down.
Table 27. Power-Down Settings
Power-Down Result
0 Power-down
1 Normal
operation
10
7-3
Sync-on-Green Slicer Threshold
This register allows the comparator threshold of the
sync-on-green slicer to be adjusted. This register
adjusts it in steps of 10 mV, with the minimum setting
equaling 10 mV (11111) and the maximum setting
equaling 330 mV (00000).
The default setting is 23, which corresponds to a
threshold value of 100 mV; for a threshold of 150 mV,
the setting should be 18.
10
2
Red Clamp Select
This bit determines whether the red channel is
clamped to ground or to midscale. For RGB video, all
three channels are referenced to ground. For YCbCr
(or YUV), the Y channel is referenced to ground, but
the CbCr channels are referenced to midscale.
Clamping to midscale actually clamps to Pin 37.
Table 28. Red Clamp Select Settings
Clamp Result
0
Clamp to ground (power-up default)
1
Clamp to midscale (Pin 37)
10
1
Green Clamp Select
This bit determines whether the green channel is
clamped to ground or to midscale.
Table 29. Green Clamp Select Settings
Clamp Result
0
Clamp to ground (power-up default)
1
Clamp to midscale (Pin 37)
10
0
Blue Clamp Select
This bit determines whether the blue channel is
clamped to ground or to midscale.
Table 30. Blue Clamp Select Settings
Clamp Result
0
Clamp to ground (power-up default)
1
Clamp to midscale (Pin 37)
11
70
Sync Separator Threshold
This register is used to set the responsiveness of the
sync separator. It sets the number of internal 5 MHz
clock periods the sync separator must count to before
toggling high or low. It works like a low-pass filter to
ignore Hsync pulses in order to extract the Vsync
signal. This register should be set to some number
greater than the maximum Hsync pulse width. The
sync separator threshold uses an internal dedicated
clock with a frequency of approximately 5 MHz.
The default for this register is 32.
12 70
Pre-Coast
This register allows the Coast signal to be applied
prior to the Vsync signal. This is necessary in cases
where pre-equalization pulses are present. The step
size for this control is one Hsync period.
The default is 0.
13 70
Post-Coast
This register allows the Coast signal to be applied
following the Vsync signal. This is necessary when
post-equalization pulses are present. The step size for
this control is one Hsync period.
The default is 0.
AD9985A
Rev. 0 | Page 24 of 32
14 7 Hsync
Detect
This bit is used to indicate when activity is detected on
the Hsync input pin (Pin 30). If Hsync is held high or
low, activity will not be detected.
Table 31. Hsync Detection Results
Detect Function
0
No activity detected
1 Activity
detected
The sync processing block diagram (Figure 14) shows
where this function is implemented.
14
6
Active Hsync (AHS)
This bit indicates which Hsync input source is being
used by the PLL (Hsync input or sync-on-green).
Bit 7 and Bit 1 in this register determine which source
is used. If both Hsync and SOG are detected, the user
can determine which has priority via Bit 3 in
Register 0x0E. The user can override this function via
Bit 4 in Register 0x0E. If the override bit is set to
Logic 1, then this bit is set to the state of Bit 3 in
Register 0x0E.
Table 32. Active Hsync Results
Bit 7
Bit 1
Bit 4
(Hsync
(SOG
Reg. 0x0E
Detect) Detect) (Override) AHS
0
0
0
Bit 3 in 0x0E
0 1 0
1
1 0 0
0
1
1
0
Bit 3 in 0x0E
X
X
1
Bit 3 in 0x0E
AHS = 0 means use the Hsync pin input for Hsync.
AHS = 1 means use the SOG pin input for Hsync.
The override bit is in Register 0x0E, Bit 4.
14
5
Detected Hsync Input Polarity Status
This bit reports the status of the Hsync input polarity
detection circuit. It can be used to determine the
polarity of the Hsync input. The detection circuit's
location is shown in the sync processing block
diagram (Figure 14).
Table 33. Detected Hsync Input Polarity Status
Hsync Polarity Status
Result
0 Negative
1 Positive
14 4 Vsync
Detect
This bit is used to indicate when activity is detected on
the Vsync input pin (Pin 31). If Vsync is held steady
high or low, activity is not detected.
Table 34. Vsync Detection Results
Detect Result
0
No activity detected
1 Activity
detected
The sync processing block diagram (Figure 14) shows
where this function is implemented.
14
3
Active Vsync (AVS)
This bit indicates which Vsync source is being used,
the Vsync input or output from the sync separator.
Bit 4 in this register determines which is active. If both
Vsync and SOG are detected, the user can determine
which has priority via Bit 0 in Register 0x0E. The user
can override this function via Bit 1 in Register 0x0E. If
the override bit is set to Logic 1, this bit is set to the
state of Bit 0 in Register 0x0E.
Table 35. Active Vsync Results
Bit 4, Reg 14H
(Vsync Detect)
Bit 1, Reg. 0x 0E
(Override)
AVS
1 0
0
0 0
1
X
1
Bit 0 in 0x0E
AVS = 0 means Vsync input.
AVS = 1 means Sync separator.
The override bit is in Register 0x0E, Bit 1.
14
2
Detected Vsync Output Polarity Status
This bit reports the status of the Vsync output polarity
detection circuit. It can be used to determine the
polarity of the Vsync output. The detection circuit's
location is shown in the sync processing block
diagram (Figure 14).
Table 36. Detected Vsync Output Polarity Status
Vsync Polarity
Status
Result
0 Active
low
1 Active
high
14 1 Sync-on-Green
Detect
This bit is used to indicate when sync activity is
detected on the sync-on-green input pin (Pin 49).
Table 37. Sync-on-Green Detection Results
Detect Result
0
No activity detected
1 Activity
detected
The sync processing block diagram (Figure 14) shows
where this function is implemented.
14
0
Detected Coast Polarity Status
This bit reports the status of the Coast input polarity
detection circuit. It can be used to determine the
polarity of the Coast input. The detection circuit's
location is shown in the sync processing block
diagram (Figure 14).
AD9985A
Rev. 0 | Page 25 of 32
Table 38. Detected Coast Input Polarity Status
Polarity Status
Result
0
Coast polarity negative
1
Coast polarity positive
This indicates that Bit 1 of Register 5 is the 4:2:2
output mode select bit.
15
1
4:2:2 Output Mode Select
A bit that configures the output data in 4:2:2 mode.
This mode can be used to reduce the number of data
lines used from 24 down to 16 for applications using
YUV, YCbCr, or YPbPr graphics signals. A timing
diagram for this mode is shown in Figure 11.
Recommended input and output configurations are
shown in Table 39 and Table 40.
Table 39. 4:2:2 Output Mode Select
Select Output
Mode
0 4:2:2
1 4:4:4
Table 40. 4:2:2 Input/Output Configuration
Channel
Input Connection
Output Format
Red V
U/V
Green Y
Y
Blue U
High
impedance
16
7
Extra PLL Divider
A bit that can add an additional divide-by-2 into the
PLL divide ratio. Enabling this function at pixel
frequencies below 20 MHz can result in improved PLL
jitter performance, as it allows the VCO to run at a
higher frequency, resulting in lower jitter.
Table 41. PLL VCO Divide
Select
PLL Divider
0 Off
1 Extra
divide-by-2
16 6-5 SOGIN
Bandwidth
Two bits that can control the bandwidth of the sync-
on-green input (SOGIN). In most applications, the
SOGIN bandwidth should be set to its maximum
(300 MHz). When there is excessive noise on SOGIN,
reducing the bandwidth can help suppress the noise.
Table 42. SOGIN Bandwidth
Select Pulses
Filtered
00 300
MHz
01 or 10
13 MHz
11 6.5
MHz
16
4
Analog Input Bandwidth
This bit controls the bandwidth of the red, green,
and blue analog inputs. In most applications, the
analog input bandwidth should be set to its maximum
(300 MHz). When there is excessive noise on the
analog inputs, reducing the bandwidth can help
suppress the noise.
Table 43. Anti-Aliasing Filter
Select Input
Bandwidth
0 300
MHz
1 7
MHz
19
7:0
Red Target Code
This specifies the targeted value of the final offset
for the red channel when auto-offset is used
(Register 0x1D, Bit 7 = 1). Default is 4.
1A
7:0
Green Target Code
This specifies the targeted value of the final offset
for the green channel when auto-offset is used
(Register 0x1D Bit 7 = 1). Default is 4.
1B
7:0
Blue Target Code
This specifies the targeted value of the final offset
for the blue channel when auto-offset is used
(Register 0x1D, Bit 7 = 1). Default is 4.
1D 7 Auto-Offset
Enable
Enables the auto-offset circuitry. Default is 0.
1D 6 Hold
Auto-Offset
Holds the offset output of the auto-offset at the
current value. Default is 0.
1D 1:0 Update
Mode
Changes the update rate of the auto-offset.
Default is 10.
Table 44. Auto-Offset Update Rate
Update Mode
Auto-Offset Update Timing
00
Every clamp cycle
01
Every 16 clamp cycles
10
Every 64 camp cycles
AD9985A
Rev. 0 | Page 26 of 32
2-WIRE SERIAL CONTROL PORT
A 2-wire serial interface control interface is provided. Two
AD9985A devices can be connected to the 2-wire serial
interface; each device has a unique address.
The 2-wire serial interface comprises a clock (SCL) and a
bidirectional data (SDA) pin. The analog flat panel interface
acts as a slave for receiving and transmitting data over the serial
interface. When the serial interface is not active, the logic levels
on SCL and SDA are pulled high by external pull-up resistors.
Data received or transmitted on the SDA line must be stable for
the duration of the positive-going SCL pulse. Data on SDA must
change only when SCL is low. If SDA changes state while SCL is
high, the serial interface interprets that action as a start or stop
sequence.
The components to serial bus operation are
Start signal
Slave address byte
Base register address byte
Data byte to read or write
Stop signal
When the serial interface is inactive (SCL and SDA are high),
communications are initiated by sending a start signal. The start
signal is a high-to-low transition on SDA while SCL is high.
This signal alerts all slave devices that a data transfer sequence
is coming.
The first eight bits of data transferred after a start signal com-
prise a 7-bit slave address (the first seven bits) and a single R/W
bit (the eighth bit). The R/W bit indicates the direction of data
transfer, read from (1) or write to (0) the slave device. If the
transmitted slave address matches the address of the device (set
by the state of the SA1-0 input pins in Table 45), the AD9985A
acknowledges by bringing SDA low on the ninth SCL pulse. If
the addresses do not match, the AD9985A does not acknowledge.
Table 45. Serial Port Addresses
Bit 7
A
6
(MSB)
Bit 6
A
5
Bit 5
A
4
Bit 4
A
3
Bit 3
A
2
Bit 2
A
1
Bit 1
A
0
1 0 0 1 1 0 0
1 0 0 1 1 0 1
DATA TRANSFER VIA SERIAL INTERFACE
For each byte of data read or written, the MSB is the first bit of
the sequence.
If the AD9985A does not acknowledge the master device during
a write sequence, the SDA remains high so the master can
generate a stop signal. If the master device does not acknowl-
edge the AD9985A during a read sequence, the AD9985A
interprets this as end-of-data. The SDA remains high so the
master can generate a stop signal.
Writing data to specific control registers of the AD9985A
requires that the 8-bit address of the control register of interest
be written after the slave address has been established. This
control register address is the base address for subsequent write
operations. The base address auto-increments by one for each
byte of data written after the data byte intended for the base
address.
Data is read from the control registers of the AD9985A in a
similar manner. Reading requires two data transfer operations:
The base address must be written with the R/W bit of the slave
address byte low to set up a sequential read operation.
Reading (the R/W bit of the slave address byte high) begins at
the previously established base address. The address of the read
register auto-increments after each byte is transferred.
To terminate a read/write sequence to the AD9985A, a stop
signal must be sent. A stop signal comprises a low-to-high
transition of SDA while SCL is high.
A repeated start signal occurs when the master device driving
the serial interface generates a start signal without first generat-
ing a stop signal to terminate the current communication. This
is used to change the mode of communication (read, write)
between the slave and master without releasing the serial
interface lines.
SDA
SCL
t
BUFF
t
STAH
t
DHO
t
DSU
t
DAL
t
DAH
t
STASU
t
STOSU
05484-
012
Figure 12. Serial Port Read/Write Timing
AD9985A
Rev. 0 | Page 27 of 32
Serial Interface Read/Write Examples
Write to one control register:
1.
Start signal
2.
Slave address byte (R/W Bit = low)
3.
Base address byte
4.
Data byte to base address
5.
Stop signal
Write to four consecutive control registers:
1.
Start signal
2.
Slave address byte (R/W bit = low)
3.
Base address byte
4.
Data byte to base address
5.
Data byte to (base address + 1)
6.
Data byte to (base address + 2)
7.
Data byte to (base address + 3)
8.
Stop signal
Read from one control register:
1.
Start signal
2.
Slave address byte (R/W bit = low)
3.
Base address byte
4.
Start signal
5.
Slave address byte (R/W bit = high)
6.
Data byte from base address
7.
Stop signal
Read from four consecutive control registers:
1.
Start signal
2.
Slave address byte (R/W bit = low)
3.
Base address byte
4.
Start signal
5.
Slave address byte (R/W Bit = high)
6.
Data byte from base address
7.
Data byte from (base address + 1)
8.
Data byte from (base Address + 2)
9.
Data byte from (base Address + 3)
10.
Stop signal
BIT 7
ACK
BIT 6
BIT 5
BIT 4
BIT 3
BIT 2
BIT 1
BIT 0
SDA
SCL
05484-014
Figure 13. Serial Interface--Typical Byte Transfer
SYNC STRIPPER
ACTIVITY
DETECT
NEGATIVE PEAK
CLAMP
COMP
SYNC
SOG
HSYNC IN
ACTIVITY
DETECT
MUX 2
HSYNC OUT
PIXEL CLOCK
MUX 1
SYNC SEPARATOR
INTEGRATOR
VSYNC
SOG OUT
HSYNC OUT
VSYNC OUT
MUX 4
VSYNC IN
1/S
PLL
HSYNC
ACTIVITY
DETECT
AD9985A
CLOCK
GENERATOR
POLARITY
DETECT
POLARITY
DETECT
POLARITY
DETECT
MUX 3
COAST
COAST
05484-
015
Figure 14. Sync Processing Block Diagram
AD9985A
Rev. 0 | Page 28 of 32
Table 46. Control of the Sync Block Muxes via the Serial Register
Mux No.
Serial Bus Control Bit
Control Bit State
Result
1 and 2
0x0E: Bit 3
0
Pass Hsync
1
Pass
sync-on-green
3
0x0F: Bit 5
0
Pass Coast
1
Pass
Vsync
4
0x0E: Bit 0
0
Pass Vsync
1
Pass sync separator signal
SYNC SLICER
The purpose of the sync slicer is to extract the sync signal from
the green graphics channel. A sync signal is not present on all
graphics systems, only those with sync-on-green. The sync
signal is extracted from the green channel in a two-step process.
First, the SOG input is clamped to its negative peak (typically,
0.3 V below the black level). Next, the signal goes to a compara-
tor with a variable trigger level, nominally 0.15 V above the
clamped level. The sliced sync is typically a composite sync
signal containing both Hsync and Vsync.
SYNC SEPARATOR
A sync separator extracts the Vsync signal from a composite
sync signal. It does this through a low-pass filter-like or
integrator-like operation. It works on the idea that the Vsync
signal stays active for a much longer time than the Hsync signal,
so it rejects any signal shorter than a threshold value, which is
somewhere between an Hsync pulse width and a Vsync pulse
width.
The sync separator on the AD9985A is simply an 8-bit digital
counter with a 5 MHz clock. It works independently of the
polarity of the composite sync signal. (Polarities are determined
elsewhere on the chip.) The basic idea is that the counter counts
up when Hsync pulses are present. But since Hsync pulses are
relatively short in width, the counter only reaches a value of N
before the pulse ends. It then starts counting down, eventually
reaching 0 before the next Hsync pulse arrives.
The specific value of N varies for different video modes, but is
always less than 255. For example, with a 1 s width Hsync, the
counter only reaches 5 (1 s/200 ns = 5). Now, when Vsync is
present on the composite sync, the counter also counts up.
However, since the Vsync signal is much longer, it counts to a
higher number M. For most video modes, M is at least 255. So,
Vsync can be detected on the composite sync signal by
detecting when the counter counts to a value higher than N.
The specific count that triggers detection (T) can be
programmed through the serial register (0x11).
Once Vsync has been detected, there is a similar process to
detect when it goes inactive. At detection, the counter first
resets to 0, then starts counting up when Vsync goes away.
Similar to the previous case, it detects the absence of Vsync
when the counter reaches the threshold count (T). In this way, it
rejects noise and/or serration pulses. Once Vsync is detected to
be absent, the counter resets to 0 and begins the cycle again.
AD9985A
Rev. 0 | Page 29 of 32
PCB LAYOUT RECOMMENDATIONS
The AD9985A is a high precision, high speed analog device.
Consequently, to get the maximum performance out of the part,
it is important to have a board with a good layout. This section
provides guidelines for designing a board using the AD9985A.
ANALOG INTERFACE INPUTS
Using the following layout techniques on the graphics inputs is
extremely important.
Minimize the trace length running into the graphics inputs.
This is accomplished by placing the AD9985A as close as
possible to the graphics VGA connector. Long input trace
lengths are undesirable because they pick up more noise from
the board and other external sources.
Place the 75 termination resistors (see Figure 1) as close as
possible to the AD9985A chip. Any additional trace length
between the termination resistors and the input of the
AD9985A increases the magnitude of reflections, which
corrupts the graphics signal.
Use 75 matched impedance traces. Trace impedances other
than 75 also increase the chance of reflections.
The AD9985A has very high input bandwidth (500 MHz).
While this is desirable for acquiring a high resolution PC
graphics signal with fast edges, it means that it also captures any
high frequency noise present. Therefore, it is important to
reduce the amount of noise that is coupled to the inputs. Avoid
running any digital traces near the analog inputs.
Due to the high bandwidth of the AD9985A, low-pass filtering
the analog inputs can sometimes help to reduce noise. (For
many applications, filtering is unnecessary.) Experiments
have shown that placing a series ferrite bead prior to the 75
termination resistor is helpful in filtering out excess noise.
Specifically, the part used was the #2508051217Z0 from Fair-
Rite, but each application can work best with a different bead
value. Alternately, placing a 100 to 120 resistor between the
75 termination resistor and the input coupling capacitor can
also be beneficial.
POWER SUPPLY BYPASSING
It is recommended to bypass each power supply pin with a
0.1 F capacitor. The exception is when two or more supply
pins are adjacent to each other. For these groupings of powers/
grounds, it is necessary to have only one bypass capacitor. The
fundamental idea is to have a bypass capacitor within about
0.5 cm of each power pin. Also, avoid placing the capacitor on
the opposite side of the PC board from the AD9985A, as that
interposes resistive vias in the path.
The bypass capacitors should be physically located between the
power plane and the power pin. Current should flow from the
power plane to the capacitor to the power pin. Do not make the
power connection between the capacitor and the power pin.
Placing a via underneath the capacitor pads, down to the power
plane, is generally the best approach.
It is particularly important to maintain low noise and good
stability of PV
D
(the clock generator supply). Abrupt changes in
PV
D
can result in similarly abrupt changes in sampling clock
phase and frequency. This can be avoided by careful attention to
regulation, filtering, and bypassing. It is highly desirable to
provide separate regulated supplies for each of the analog
circuitry groups (V
D
and PV
D
).
Some graphic controllers use substantially different levels of
power when active (during active picture time) and when idle
(during horizontal and vertical sync periods). This can result in
a measurable change in the voltage supplied to the analog
supply regulator, which can, in turn, produce changes in the
regulated analog supply voltage. This can be mitigated by
regulating the analog supply, or at least PV
D
, from a different,
cleaner power source (for example, from a 12 V supply).
It is recommended to use a single ground plane for the entire
board. Experience has repeatedly shown that the noise
performance is the same or better with a single ground plane.
Using multiple ground planes can be detrimental because each
separate ground plane is smaller, and long ground loops can
result.
When using separate ground planes is unavoidable, it is
recommended to minimally place a single ground plane under
the AD9985A. The location of the split should be at the receiver
of the digital outputs. For this case, it is even more important to
place components wisely because the current loops are much
longer (current takes the path of least resistance). Figure 15
shows an example of a current loop.
A
N
A
LO
G
GR
O
UN
D P
LAN
E
POWER PLANE
AD9985A
D
IGIT
AL
O
U
T
P
U
T
TR
AC
E
DIG
ITAL
GROU
ND PLANE
DIGITAL DATA R
ECEIV
ER
05484-016
Figure 15. Current Loop
PLL
Place the PLL loop filter components as close to the FILT pin as
possible.
Do not place any digital or other high frequency traces near
these components.
Use the values suggested in the data sheet with 10% tolerances
or less.
AD9985A
Rev. 0 | Page 30 of 32
OUTPUTS (BOTH DATA AND CLOCKS)
Try to minimize the trace length that the digital outputs have to
drive. Longer traces have higher capacitance, which requires
more current, which causes more internal digital noise. Shorter
traces reduce the possibility of reflections.
Adding a series resistor of value 22 to 100 can suppress
reflections, reduce EMI, and reduce the current spikes inside of
the AD9985A. However, if 50 traces are used on the PCB, the
data outputs should not need resistors. A 22 resistor on the
DATACK output should provide good impedance matching
that reduces reflections. If series resistors are used, place them
as close as possible to the AD9985A pins (but try not to add vias
or extra length to the output trace in order to get the resistors
closer).
If possible, limit the capacitance that each of the digital outputs
drives to less than 10 pF. This can easily be accomplished by
keeping traces short and by connecting the outputs to only one
device. Loading the outputs with excessive capacitance increases
the current transients inside of the AD9985A, creating more
digital noise on its power supplies.
DIGITAL INPUTS
The digital inputs on the AD9985A were designed to work with
3.3 V signals, but are tolerant of 5.0 V signals. Therefore, no
extra components need to be added if using 5.0 V logic.
Any noise that gets onto the Hsync input trace adds jitter to the
system. Therefore, minimize the trace length and do not run
any digital or other high frequency traces near it.
VOLTAGE REFERENCE
Bypass the voltage reference with a 0.1 F capacitor. Place it as
close as possible to the AD9985A pin. Make the ground
connection as short as possible.
AD9985A
Rev. 0 | Page 31 of 32
OUTLINE DIMENSIONS
COMPLIANT TO JEDEC STANDARDS MS-026-BEC
1.45
1.40
1.35
0.15
0.05
0.20
0.09
0.10 MAX
COPLANARITY
VIEW A
ROTATED 90 CCW
SEATING
PLANE
7
3.5
0
61
60
1
80
20
41
21
40
VIEW A
1.60
MAX
0.75
0.60
0.45
16.20
16.00 SQ
15.80
14.20
14.00 SQ
13.80
0.65
BSC
LEAD PITCH
0.38
0.32
0.22
TOP VIEW
(PINS DOWN)
PIN 1
Figure 16. 80-Lead Low Profile Quad Flat Package [LQFP]
(ST-80-2)
Dimensions shown in millimeters
ORDERING GUIDE
Model
Temperature Range
Package Description
Package Option
AD9985ABSTZ-110
1
40C to +85C
80-lead LQFP
ST-80-2
AD9985AKSTZ-110
1
0C to 70C
80-lead LQFP
ST-80-2
AD9985AKSTZ-140
1
0C to 70C
80-lead LQFP
ST-80-2
AD9985A/PCB
Evaluation
Board
1
Z = Pb-free part.
AD9985A
Rev. 0 | Page 32 of 32
NOTES
2005 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05484-0-7/05(0)
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